By Feng Wang, Ramesh Harjani
Oversampled A/D converters became very hot lately. a few of their merits comprise comfortable specifications for anti-alias filters, comfy specifications for part matching, excessive answer and compatibility with electronic VLSI know-how. there's a major quantity of literature discussing the primary, conception and implementation of assorted oversampled converters. Such converters are inclined to proceed to proliferate within the foreseeable destiny. also, extra lately there was nice curiosity in low voltage and coffee strength circuit layout. New layout strategies were proposed for either the electronic area and the analog area. either traits aspect to the significance of the low-power layout of oversampled A/D converters.
regrettably, there was no systematic research of the optimum layout of modulators for oversampled converters. layout has more often than not fascinated about new architectures with little recognition being paid to optimization.
The aim of Design of Modulators for Oversampled Converters is to improve a strategy for the optimum layout of modulators in oversampled converters. the first concentration of the presentation is on minimizing strength intake and knowing and restricting the nonlinearities that bring about such converters.
Design of Modulators for Oversampled Converters deals a quantitative justification for some of the layout tradeoffs and serves as a consultant for designing low-power hugely linear oversampled converters. Designof Modulators for Oversampled Converters will function a important consultant for circuit layout practitioners, college researchers and graduate scholars who're drawn to this fast-moving area.
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Additional resources for Design of Modulators for Oversampled Converters
Slewing occurs when the differential input voltage is larger than the ~ Vd (II gm) of the differential pair transistors. 20. 8 Bias current behavior shut off while the other one is completely on. The entire bias current (Ids5) is used to charge or discharge the load capacitor. 26 is used for this analysis. The behavior is similar for other opamp circuits and only differs in the details. For example, for the two-stage Miller compensated opamp, during the slew period, the bias current charges and discharges the compensation capacitor rather than just the load capacitor.
57) where 9m(t) = l+(t~~';)/to is the transconductance of the input differential pair, t is the time after the input is applied, and tr is the time interval between the rising edge of 24 shows the total transient time vs. input voltage for both the class A and dynamic opamps under the same power consumption constraint. In this figure, one can notice that the total settling time for the dynamic opamp is always less than that for the class A opamp. In other words, for the same total transient time, dynamic opamps will consume less power. This can be understood as follows. ~ ++ 1a'" XX + + x + ;Ie x x ~ t;j ..... 24. 9 Total transient time for different input steps voltage for a dynamic opamps increases more rapidly than that of a class A opamp.
24 shows the total transient time vs. input voltage for both the class A and dynamic opamps under the same power consumption constraint. In this figure, one can notice that the total settling time for the dynamic opamp is always less than that for the class A opamp. In other words, for the same total transient time, dynamic opamps will consume less power. This can be understood as follows. ~ ++ 1a'" XX + + x + ;Ie x x ~ t;j ..... 24. 9 Total transient time for different input steps voltage for a dynamic opamps increases more rapidly than that of a class A opamp.